Analog linearization of resistance temperature detectors
Published by: Jasmine
On: 26 Jun, 2019
Viewed:121 times - 5 hour, 50 minute, 52 second ago
Downloaded: 0 times -
Resistance temperature detectors (RTDs) are commonly used in industrial and scien-tific temperature measurements. The most common types are pure platinum (Pt) formed into wire or evaporated in a thin film on a substrate. They rely on the funda-men...
Resistance temperature detectors (RTDs) are commonly used in industrial and scien-tific temperature measurements. The most common types are pure platinum (Pt) formed into wire or evaporated in a thin film on a substrate. They rely on the funda-mental temperature-dependent resistance properties of this noble metal. They are very stable and useful at temperatures ranging from cryogenic to over 800°C. A wide range of physical configurations, resistance ranges and accuracies is avail-able.1 The commonly used notation “Pt100” indicates a 100-W resistance at 0°C. The relationship between the RTD’s resistance and temperature is described by the Callendar-Van Dusen equation,RRTD = R0[1 + AT + BT2 + C(T – 100)T3],whose values are defined as follows:R0 is a 100-W resistance at 0°C (Pt100)A = 3.9083 × 10–3B = –5.775 × 10–7C = 0 for T > 0°C, or C = –4.23225 × 10–12 for T < 0°C
The resistance of a Pt100 RTD increases with tempera-ture at approximately 0.39%/°C. While they are far more linear than thermocouples, RTDs have a significant second-order nonlinearity of approximately 0.38% per 100°C measurement range (see Figure 1). This nonlinearity is often corrected digitally, but there are many applications for purely analog processing and linearization of the RTD.This article explains an analog technique for linearization of the RTD. The same technique is also used with bridge sensors such as pressure and load cells. The principles can be applied to other ratiometric devices with primarily second-order nonlinearity; i.e., any sensor or system with an output that is proportional to an excita-tion voltage or current.The exaggerated graph in Figure 2 shows that the temperature coefficient decreases with increasing temperature, producing an upward bow in the middle. Above 0°C, standardized data for the Pt100 has a purely second-order or para-bolic function. Assuming calibration at two end-point temperatures, this produces an error that is greatest at the midpoint temperature.
When the RTD is excited with a current source, the resulting RTD voltage is directly proportional to the resist-ance, yielding the same nonlinearity. If, however, the excita-tion current is gradually increased as the RTD temperature is increased, the nonlinearity can be greatly reduced. Figure 2 shows an increasing excitation current derived from the output of the amplified RTD voltage. This current is, in effect, a controlled amount of positive feedback. It yields an interesting “chicken-or-egg” dichotomy: The RTD voltage at the input of the amplifier is linearized when the output of the amplifier is linearized—and vice versa. The correct amount of positive feedback results in both.When positive feedback is optimized, a much smaller s-shaped error remains with nearly equal negative and positive values, reaching maximums at ¼ and ¾ full scale (see Figure 3). This primarily third-order nonlinearity does not come from the RTD but is an artifact of the linearization tech-nique. Its magnitude depends on the tem-perature range chosen for linearization. Figure 3 shows the initial nonlinearity error for a –100°C to +800°C temperature range—a 900°C span. The 3.7% RTD non-linearity at midscale is reduced to approxi-mately ±0.11%, a 33:1 improvement. The improvement is even greater for narrow temperature ranges, approaching 150:1 for a 200°C range.
The use of positive feedback might raise the concern of possible circuit instability. The magnitude of this feedback is small enough, however, to have negligible effect on the stability of commonly used circuits.Figure 4 shows a practical implementation of an RTD. R1 provides the primary excita-tion current from VREF, a stable voltage reference. R5 provides the temperature-varying component of excitation current from the output of A1. R2, R3, and R4 set the required amplifier gain and offset to produce the desired output-voltage range. The Texas Instruments (TI) OPA188* shown in this example is a new low-noise, chopper-stabilized operational amplifier that contributes negligible error to the circuit. Its very low and stable offset voltage makes it a possible upgrade to TI’s OPA277 precision industrial amplifier.The resistor values to achieve best correction can be calculated with iterative techniques. Many designers might optimize this type of circuit by using creative calculations or approximations. A closed-form solution is possible by solving the nodal equation that relates the RTD voltage, RTD resistance, VREF, R1, R5, and VOUT:
Three conditions must be met to achieve zero error at the calibration endpoint tem-peratures and the midpoint temperature. Three separate variations of the preceding equation are written to describe the three zero-error conditions and are solved simul-taneously for the only unknown variable, R5. The resistance of the RTD at the mid-point temperature is not halfway between the endpoint resistances. This midpoint condition holds the key to the solution for best linearity correction.
The math yields three results for R5; only one is a positive resistance. The expression for R5 is very long and impractical to pre-sent here. To download an Excel® work-sheet that provides the calculations, go to http://www.ti.com/lit/zip/SLYT442 and click Open to view the WinZip® directory online (or click Save to download the WinZip file for offline use). Then open the file RTD_Linearization_v7.xls to view the calculation worksheet. This closed-form solution is intellectually satisfying and avoids possible problems with convergence, but the results are no better than those produced with iterative calculations. Practical implemen-tations often require trimming of resistors for calibration because accurate, non-standard values are often required. SPICE simulation can help determine actual performance with the nearest standard values. The WinZip file download listed above also includes two RTD simulation examples in TINA-TI™ SPICE files. One file implements an RTD linearization circuit based on an operational amplifier, and the other file is based on an instrumentation amplifier. Please see Reference 2 for more information on an RTD simulator for SPICE.
Figure 5 shows that uncorrected non-linearity of the RTD increases as the cali-brated temperature range is increased, reaching approximately 2% for a 500°C span. The variation in the RTD’s excitation current to compensate for this nonlinearity is approx-imately four times the nonlinearity. Thus, for a 500°C measurement span, the excitation current increases by approximately 8% from low-scale temperature to full scale.
Low-resistance connections to the RTD are crucial in maintaining accuracy with this circuit. For this reason, high-resistance RTDs such as Pt1000 or Pt5000 may be most practical. With a four-wire (or Kelvin) connection to the RTD and an additional operational amplifier, errors induced by wire resistance can be eliminated.An integrated instrumentation amplifier with a three-wire RTD connection can provide an alternative solution (see Figure 6). In the three-wire connection, two connections are used on the ground side of the RTD. Equal currents flowing in equal line resistances create a common-mode input voltage that is rejected by the instrumentation amplifier. Current flowing in the ground-wire connection also creates a common-mode voltage. Note that the cur-rents in signal connections are not precisely equal. They differ due to the varying linearity correction current from R5. Nevertheless, this configuration removes most of the error that is due to line resistance.
Other sensor types
Bridge sensors such as strain gauges and load cells fre-quently require linearization with similar techniques. Voltage excitation is generally used for these applications, but the concept is the same. Excitation voltage is varied with amplifier output voltage. These sensors can have a downward bowing nonlinearity requiring that the excita-tion voltage decrease as pressure increases. Furthermore, nonlinearity may vary significantly from unit to unit, so individual calibration may be required.
TI uses variable excitation for linearization in several inte-grated circuits intended for RTDs and bridge sensors (see Table 1). Some circuits are designed specifically for remote sensors with two-wire, 4- to 20-mA current-loop output. XTR106 and PGA309 provide voltage excitation, which is preferred for many strain-gauge bridge-sensor applications. Though designed for specific sensor types, these devices have been successfully adapted to a variety of sensor applications, with and without variable excitation for linearization. -------------------------------------------------------
Monolithic integration techniques allow a reduction of production costs for hybrid and modular circuits. For instrumentation ampliflers there are circuit alternatives to those in Figures 3.39 and 3...
The circuit in Figure 3.40 is the classic implementation for an instrumentation amplifier. Its analysis when the three op amps are ideal leads to.. By eliminatingV6, Vn, and Vc in the preceding equ...
Most resistance sensor bridges are supplied by a grounded voltage or curreht source. Therefore the amplifier at the bridge's output should not have any of its input terminals grounded. In addition ...
Definition - Shunt calibration is the known, electrical unbalancing of a strain gage bridge, by means of a fixed resistor that is placed, or “shunted”, across a leg of ...
Equation (3.31) shows that the sensitivity of a sensor bridge depends on the supply voltage V, on the sensor's resistance under no load condit-:ns Rs,
and on the ratio k between the resistance...
Wheatstone bridge circuits have been in the field for a very long time and still are among the first choices for front-end sensors. Whether the bridges are symmetric or asymmetric, balanced or unba...
As the fastest growing demand of circuit and wiring diagram for automotive and electronics on internet based on different uses such as electronic hobbyists, students, technicians and engineers than we decided to provide free circuit and wiring diagram base on your needed.
To find circuit and wiring diagram now a day its easy. E-learning through internet as a right place to search an exact circuit and wiring diagram of your choice and it's much fun and knowledgable. On internet you will find thousands of electronic circuit diagrams some are very good designed and some are not. So you have to modify them to make them according to your needs but some circuits are ready to make and require no changes.
There are many categories of circuit and wiring diagrams like automotive, audio circuits, radio & RF circuits, power supply circuits, light circuits, telephone circuits, timer circuits, battery charger circuits etc. There are many types of circuit and wiring diagrams some are very easy to build and some are very complicated, some are so small and some contain huge list of parts.
We provides free best quality and good designed schematic diagrams our diagrams are free to use for all electronic hobbyists, students, technicians and engineers. We also provides a full educational system to students new to electronics. If you are new to electronics you are a student or a electronic hobbyist and want to increase your knowledge in electronics or want to understand electronics in a very easy way so this is the right place for you we provide electronics beginner guide tutorials to easily understand complicated electronic theory. Our mission is to help students and professionals in their field.